Method and apparatus for transmitting channel quality control information in wireless access system

ABSTRACT

Methods and devices for transmitting or receiving channel quality control information through a physical uplink shared channel (PUSCH) in a wireless access system that supports hybrid automatic retransmit request (HARQ) are discussed. The method in one embodiment performed by a user equipment (UE) includes receiving a physical downlink control channel (PDCCH) signal including an initial uplink grant, transmitting uplink data using two transport blocks based on the initial uplink grant, receiving a negative acknowledgement (NACK) information for one of the two transport blocks, and transmitting a channel quality control information along with the one of the two transport blocks which is retransmitted according to the NACK information or a new transport block through the PUSCH to which the HARQ is applied. A number of coded symbols required to transmit the channel quality control information (Q′) is calculated based on the initial uplink grant.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation of copending U.S. patent applicationSer. No. 13/396,406, filed on Feb. 14, 2012, which claims priority toKorean Patent Application No. 10-2012-0001527, filed on Jan. 5, 2012 andto U.S. Provisional Application Ser. No. 61/443,207, filed on Feb. 15,2011. The contents of all of these applications are hereby incorporatedby reference as fully set forth herein in their entirety.

FIELD OF INVENTION

The present invention relates to a wireless access system, and moreparticularly, to a method and apparatus for transmitting uplink channelinformation (UCI) including channel quality control information in acarrier aggregation environment (i.e., a multi-component carrierenvironment). The invention relates to a method and apparatus forobtaining the number of resource elements allocated to UCI when the UCIpiggybacks on a physical uplink shared channel (PUSCH).

DISCUSSION OF THE RELATED ART

A 3GPP LTE (3rd Generation Partnership Project Long Term Evolution;Rel-8 or Rel-9) system (hereinafter referred to as an LTE system)employs multi-carrier modulation (MCM) that splits a single componentcarrier (CC) into multiple bands and uses the multiple bands. However, a3PP LTE-Advanced system (hereinafter referred to as an LTE-A system) canuse carrier aggregation (CA) that aggregates one or more CCs to supporta system bandwidth wider than that of the LTE system. The CA can bereplaced by carrier matching, multi-CC environment, or multi-carrierenvironment.

In a single CC environment such as an LTE system, a description is madeof only a case in which uplink control information (UCI) and data aremultiplexed using a plurality of layers on one CC.

In a CA environment, however, one or more CCs can be used and the numberof pieces of UCI can be increased to a multiple of the number of CCs.For example, while rank indication information has 2 or 3 bits in theLTE system, it can have a maximum of 15 bits in the LTE-A system sincethe bandwidth can be extended to up to 5 CCs.

In this case, UCI having a size of 15 bits cannot be transmitted using aUCI transmission method defined in the LTE system and cannot be encodedeven when Reed-Muller (RM) code is used. Accordingly, the LTE-A systemneeds a new method for transmitting UCI having a large size.

SUMMARY OF THE INVENTION

Accordingly, the present invention is directed to methods andapparatuses for transmitting channel quality control information, whichsubstantially obviates one or more of the problems due to limitationsand disadvantages of the related art.

An object of the present invention is to provide a method forefficiently encoding and transmitting UCI in a multi-carrier environment(or CA environment).

Another object of the present invention is to provide a method forobtaining the number of resource elements (REs) allocated to UCI whenthe UCI piggybacks on a PUSCH.

Another object of the present invention is to provide a method forcalculating the number of REs required to transmit channel qualitycontrol information (i.e., CQI and/or PMI) when UCI is retransmittedusing two or more transport blocks (TBs).

Another object of the present invention is to provide a user equipment(UE) and/or a base station apparatus for supporting the above-describedmethods.

Technical problems to be solved by the present invention are not limitedto the above-mentioned technical problem, and other technical problemsnot mentioned above can be clearly understood by one skilled in the artfrom the following description.

To achieve these and other advantages and in accordance with the purposeof the present invention, as embodied and broadly described, theembodiments of the present invention disclose methods and apparatusesfor transmitting UCI including channel quality control information in aCA environment.

In one aspect of the present invention, a method for transmittingchannel quality control information using two transport blocks in awireless access system that supports hybrid automatic retransmit request(HARQ) includes the steps of receiving a physical downlink controlchannel (PDCCH) signal including downlink control information (DCI),calculating the number of coded symbols, Q′, required to transmit thechannel quality control information using the DCI, and transmitting thechannel quality control information through a physical uplink sharedchannel (PUSCH) on the basis of the number of coded symbols.

In another aspect of the present invention, a UE for transmittingchannel quality control information using two transport blocks in awireless access system that supports HARQ includes a transmission modulefor transmitting a radio signal, a reception module for receiving aradio signal, and a processor configured to support transmission of thechannel quality control information. The UE may receive a PDCCH signalincluding DCI, calculate the number of coded symbols, Q′, required totransmit channel quality control information using the DCI, and transmitthe channel quality control information over a PUSCH on the basis of thenumber of coded symbols.

The number of coded symbols, Q′, may be calculated using

${\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {{initial}{(x)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(x)}}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}^{(x)}}{Q_{m}^{(x)}}}} \right)},$and the DCI may include information M_(sc) ^(PUSCH-initial(x)) on thenumber of subcarriers for a first transport block for transmitting thechannel quality control information, information C^((x)) on the numberof code blocks related to the first transport block, and informationK_(r) ^((x)) on the size of the code blocks, wherein x denotes an indexof one of the two transport blocks.

The first transport block may be a transport block having a highermodulation and coding scheme (MCS) level from the two transport blocks.If the two transport blocks have the same MCS level, the first transportblock may be the first one of the two transport block.

In the step of the transmitting of the channel quality controlinformation, the UE is able to piggyback the channel quality controlinformation on uplink data retransmitted using HARQ and transmit theuplink data with the channel quality control information.

The UE may compute information about the uplink data using G=N_(L)^((x))·(N_(symb) ^(PUSCH)·M_(sc) ^(PUSCH)·Q_(m) ^((x))−Q_(CQI)−Q_(RI)^((x))).

In another aspect of the present invention, a method for receivingchannel quality control information using two transport blocks in awireless access system that supports HARQ includes enabling an eNB totransmit a PDCCH signal including DCI to a UE, and receiving the channelquality control information through a PUSCH from the UE.

The number of coded symbols, Q′, required to transmit the channelquality control information, may be calculated using

${\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {{initial}{(x)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(x)}}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}^{(x)}}{Q_{m}^{(x)}}}} \right)},$and the DCI may include information M_(sc) ^(PUSCH-initial(x)) on thenumber of subcarriers for a first transport block for transmitting thechannel quality control information, information C^((x)) on the numberof code blocks related to the first transport block, and informationK_(r) ^((x)) on the size of the code blocks, wherein x denotes an indexof one of the two transport blocks.

In another aspect of the present invention, the first transport blockmay be a transport block having a higher MCS level from the twotransport blocks. If the two transport blocks have the same MCS level,the first transport block may be the first one of the two transportblocks.

The channel quality control information may piggyback on uplink dataretransmitted using HARQ to be received. Information about the uplinkdata may be calculated by G=N_(L) ^((x))·(N_(symb) ^(PUSCH)·M_(sc)^(PUSCH)·Q_(m) ^((x))−Q_(CQI)−Q_(RI) ^((x))).

The above embodiments are part of preferred embodiments of the presentinvention. Obviously, it is to be understood to those having ordinaryknowledge in the art that various embodiments having the technicalfeatures of the present invention can be implemented on the detaileddescription of the present invention as set forth herein.

According to exemplary embodiments of the present invention, thefollowing advantages can be obtained.

UCI can be efficiently encoded and transmitted in a multi-carrierenvironment (or CA environment).

Furthermore, the number of REs required to transmit CQI and/or PMI canbe correctly calculated for each TB when UCI is transmitted using two ormore TBs.

Moreover, when channel quality control information (CQI/PMI) piggybackson a PUSCH, the number of REs required to transmit the CQI/PMI can beexactly calculated for each TB. Particularly, when initial resourcevalues of two TBs are different from each other due to HARQretransmission, the number of REs required to transmit CQI/PMI through aPUSCH can be correctly calculated.

It is to be understood that both the foregoing general description andthe following detailed description of the present invention areexemplary and explanatory and are intended to provide furtherexplanation of the invention as claimed.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings, which are included to provide a furtherunderstanding of the invention and are incorporated in and constitute apart of this application, illustrate embodiments of the invention andtogether with the description serve to explain the principle of theinvention. In the drawings:

FIG. 1 is a view referred to for describing physical channels used in a3GPP LTE system and a general signal transmission method using thephysical channels;

FIG. 2 illustrates a configuration of a user equipment (UE) and a signalprocessing procedure for transmitting an uplink signal;

FIG. 3 illustrates a configuration of a base station (BS) and a signalprocessing procedure for transmitting a downlink signal;

FIG. 4 is a view referred to for describing a configuration of a UE andSC-FDMA and OFDMA schemes;

FIG. 5 is a view referred to for describing a signal mapping method in afrequency domain to satisfy single carrier properties in the frequencydomain;

FIG. 6 is a block diagram for describing a reference signal transmissionprocedure for demodulating a transmit signal according to SC-FDMA;

FIG. 7 shows a symbol position to which a reference signal is mapped ina subframe structure according to SC-FDMA;

FIG. 8 shows a signal processing procedure for mapping DFT processoutput samples to a single carrier in clustered SC-FDMA;

FIGS. 9 and 10 show a signal processing procedure for mapping DFTprocess output samples to multiple carriers in clustered SC-FDMA;

FIG. 11 shows a signal processing procedure of segmented SC-FDMA;

FIG. 12 illustrates a structure of an uplink subframe that can be usedin embodiments of the present invention;

FIG. 13 illustrates a procedure of processing UL-SCH data and controlinformation that can be used in embodiments of the present invention;

FIG. 14 illustrates an exemplary method for multiplexing UCI and UL-SCHdata on a PUSCH;

FIG. 15 is a flowchart illustrating a procedure of multiplexing controlinformation and UL-SCH data in a multiple input multiple output (MIMO)system;

FIGS. 16 and 17 illustrate an exemplary method for multiplexing aplurality of UL-SCH TBs and UCI by a UE according to an embodiment ofthe present invention;

FIG. 18 illustrates a method for mapping physical resource elements totransmit uplink data and UCI;

FIG. 19 illustrates a method for transmitting UCI according to anembodiment of the present invention;

FIG. 20 illustrates a method for transmitting UCI according to anotherembodiment of the present invention; and

FIG. 21 shows apparatuses for implementing the methods described inFIGS. 1 to 20.

DETAILED DESCRIPTION OF THE EMBODIMENTS

Exemplary embodiments of the present invention provide a method andapparatuses for transmitting and receiving UCI in a CA environment (ormulti-component carrier environment). In addition, exemplary embodimentsof the present invention provide methods and apparatuses fortransmitting and receiving RI information, and methods and apparatusesfor applying an error detection code to UCI.

The embodiments of the present invention described below arecombinations of elements and features of the present invention inspecific forms. The elements or features may be considered selectiveunless otherwise mentioned. Each element or feature may be practicedwithout being combined with other elements or features. Further, anembodiment of the present invention may be constructed by combiningparts of the elements and/or features. Operation orders described inembodiments of the present invention may be rearranged. Someconstructions or elements of any one embodiment may be included inanother embodiment and may be replaced with corresponding constructionsor features of another embodiment.

In the description of the attached drawings, a detailed description ofknown procedures or steps of the present invention will be avoided lestit should obscure the subject matter of the present invention. Inaddition, procedures or steps that could be understood by those skilledin the art will not be described either.

In the embodiments of the present invention, a description has beenmainly made of a data transmission and reception relationship between aBS and a UE. A BS refers to a terminal node of a network, which directlycommunicates with a UE. A specific operation described as beingperformed by the BS may be performed by an upper node of the BS.

Namely, it is apparent that, in a network comprised of a plurality ofnetwork nodes including a BS, various operations performed forcommunication with a UE may be performed by the BS, or network nodesother than the BS. The term ‘BS’ may be replaced with a fixed station, aNode B, an eNode B (eNB), an ABS (Advanced Base Station), an accesspoint, etc.

The term UE may be replaced with the terms MS (Mobile Station), SS(Subscriber Station), MSS (Mobile Subscriber Station), AMS (AdvancedMobile Station), mobile terminal, etc. Especially, it should be notedthat the terms ‘eNB’ and ‘eNode-B’ are used interchangeably and theterms ‘UE’ and ‘terminal’ are interchangeably used in the embodiments ofthe present invention.

A transmitter is a fixed and/or mobile node that provides a data orvoice service and a receiver is a fixed and/or mobile node that receivesa data or voice service. Therefore, an MS may serve as a transmitter anda BS may serve as a receiver, on uplink. Likewise, the MS may serve as areceiver and the BS may serve as a transmitter, on downlink.

The embodiments of the present invention are supported by standarddocuments disclosed for at least one of wireless access systemsincluding IEEE 802.xx systems, a 3GPP system, a 3GPP LTE system, and a3GPP2 system. In particular, the embodiments of the present inventionare supported by 3GPP TS 36.211, 3GPP TS 36.212, 3GPP TS 36.213, and3GPP TS 36.321 documents. The steps or parts, which are not described toclearly reveal the technical idea of the present invention, in theembodiments of the present invention may be supported by the abovedocuments. All terms used in the embodiments of the present inventionmay be explained by the standard documents.

Reference will now be made in detail to the preferred embodiments of thepresent invention with reference to the accompanying drawings. Thedetailed description, which will be given below with reference to theaccompanying drawings, is intended to explain exemplary embodiments ofthe present invention, rather than to show the only embodiments that canbe implemented according to the invention. Specific terms used for theembodiments of the present invention are provided to aid inunderstanding of the present invention. These specific terms may bereplaced with other terms within the scope and spirit of the presentinvention.

The embodiments of the present invention may be used in various wirelessaccess technologies, such as CDMA (Code Division Multiple Access), FDMA(Frequency Division Multiple Access), TDMA (Time Division MultipleAccess), OFDMA (Orthogonal Frequency Division Multiple access), andSC-FDMA (Single Carrier Frequency Division Multiple Access).

CDMA may be implemented with radio technology such as UTRA (UniversalTerrestrial Radio Access) or CDMA2000. TDMA may be implemented withradio technology such as GSM (Global System for Mobilecommunications)/GPRS (General Packet Radio Service)/EDGE (Enhanced DataRates for GSM Evolution). OFDMA may be implemented with radio technologysuch as IEEE 802.11 (Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802.20, andE-UTRA (Evolved UTRA).

UTRA is part of a UMTS (Universal Mobile Telecommunications System).3GPP LTE is a part of Evolved UMTS (E-UMTS), which uses E-UTRA. 3GPP LTEemploys OFDMA on downlink and uses SC-FDMA on uplink. LTE-A (Advanced)is an evolved version of 3GPP LTE. The following embodiments of thepresent invention mainly describe examples of the technicalcharacteristics of the present invention as applied to the 3GPPLTE/LTE-A systems. However, this is merely exemplary and the presentinvention can be applied to IEEE 802.16e/m systems.

1. 3GPP LTE/LTE-A System

In a wireless access system, a UE receives information from a BS througha downlink and transmits information to the BS through an uplink.Information transmitted and received between the UE and the BS includesgeneral data information and control information. A variety of physicalchannels are provided according to type/use of information transmittedand received between the UE and the BS.

FIG. 1 is a view referred to for describing physical channels used in a3GPP LTE system and a signal transmission method using the same.

When a UE is powered on or newly enters a cell, the UE performs aninitial cell search operation including synchronization with a BS inS101. To implement this, the UE receives a primary synchronizationchannel (P-SCH) and a secondary synchronization channel (S-SCH) tosynchronize with the BS and acquires information such as cell ID.

Then, the UE can acquire broadcast information in the cell by receivinga physical broadcast channel (PBCH) signal from the BS. The UE canreceive a downlink reference signal (DL RS) in the initial cell searchoperation to check a downlink channel state.

Upon completion of the initial cell search, the UE receives a physicaldownlink control channel (PDCCH) and a physical downlink shared channel(PDSCH) according to PDCCH information to acquire more detailed systeminformation in S102.

Subsequently, the UE can perform a random access procedure, S103 toS106, in order to complete access to the BS. To achieve this, the UEtransmits a preamble through a physical random access channel (PRACH)(S103) and receives a response message to the preamble through a PDCCHand a PDSCH corresponding to the PDCCH (S104). In the case ofcontention-based random access, the UE can perform a contentionresolution procedure of transmitting an additional PRACH signal (S105)and receiving a PDCCH signal and a PDSCH signal corresponding to thePDCCH signal (S106).

Upon completion of the random access procedure, the UE can perform ageneral uplink/downlink signal transmission procedure of receiving aPDCCH signal and/or a PDSCH signal (S107) and transmitting a physicaluplink shared channel (PUSCH) and/or a physical uplink control channel(PUCCH) (S108).

Control information transmitted from a UE to a BS is referred to asuplink control information (UCI). UCI includes HARQ-ACK/NACK (HybridAutomatic Repeat and request Acknowledgement/Negative-ACK), SR(Scheduling Request), CQI (Channel Quality Indication), PMI (PrecodingMatrix Indicator), RI (Rank Information), etc.

In the LTE system, UCI is periodically transmitted through a PUCCH, ingeneral. However, UCI can be transmitted through a PUSCH when controlinformation and traffic data need to be simultaneously transmitted. Inaddition, UCI can be non-periodically transmitted through a PUSCH at therequest/instruction of a network.

FIG. 2 is a view referred to for describing a configuration of a UE anda signal processing procedure of the UE to transmit an uplink signal.

To transmit an uplink signal, a scrambling module 210 of the UE canscramble a transmitted signal using a UE-specific scramble signal. Thescrambled signal is input to a modulation mapper 202 and modulated intoa complex symbol using BPSK (Binary Phase Shift Keying), QPSK(Quadrature Phase Shift Keying), or 16QAM/64QAM (Quadrature AmplitudeModulation). The complex symbol is processed by a conversion precoder203 and applied to a resource element mapper 204. The resource elementmapper 204 can map the complex symbol to a time-frequency resourceelement. The signal processed in this manner can be transmitted to theBS through an antenna via an SC-FDMA signal generator 205.

FIG. 3 is a view referred to for describing a configuration of a BS anda signal processing procedure of the BS to transmit a downlink signal.

In a 3GPP LTE system, the BS can transmit one or more codewords througha downlink. Each codeword can be processed into a complex symbol througha scrambling module 301 and a modulation mapper 302 as in the uplinkshown in FIG. 2. The complex symbol is mapped by a layer mapper 303 to aplurality of layers each of which can be multiplied by a precodingmatrix by a precoding module 304 to be allocated to each transmitantenna. A transmission signal for each antenna, processed as above, ismapped by a resource element mapper 305 to a time-frequency resourceelement. The mapped signal is subjected to an OFDM signal generator 306and transmitted through each antenna.

When a UE transmits a signal on uplink in a radio communication system,PAPR (Peak-to-Average Ratio) becomes a problem, compared to a case inwhich a BS transmits a signal on downlink. Accordingly, SC-FDMA is usedfor uplink signal transmission, as described above with reference toFIGS. 2 and 3, while OFDMA is used for downlink signal transmission.

FIG. 4 is a view referred to for describing a configuration of a UE andSC-FDMA and OFDMA.

A 3GPP system (e.g. LTE system) employs OFDMA on downlink and usesSC-FDMA on uplink. Referring to FIG. 4, both a UE for uplink signaltransmission and a BS for downlink signal transmission include aserial-to-parallel converter 401, a subcarrier mapper 403, an M-pointIDFT module 404, and a cyclic prefix (CP) addition module 406.

The UE for transmitting a signal through SC-FDMA additionally includesan N-point DFT module 402. The N-point DFT module 402 offsets theinfluence of IDFT of the M-point IDFT module 404 on a transmissionsignal such that the transmission signal has single carrier properties.

FIG. 5 illustrates a signal mapping method in a frequency domain tosatisfy single carrier properties in the frequency domain.

FIG. 5( a) represents a localized mapping method and FIG. 5( b)represents a distributed mapping method. Clustered SC-FDMA, which is amodified version of SC-FDMA, classifies DFT process output samples intosub-groups and discretely maps the sub-groups to the frequency domain(or subcarrier domain) during a subcarrier mapping procedure.

FIG. 6 is a block diagram illustrating a procedure of transmitting areference signal (RS) for demodulating a transmission signal accordingto SC-FDMA.

The LTE standard (e.g. 3GPP release 9) defines that an RS is generatedin a frequency domain (S610) without being subjected to DFT, mapped to asubcarrier (S620), IFFT-processed (S630), subjected to CP attachment(S640), and then transmitted while data is transmitted in such a mannerthat a signal generated in a time domain is converted to a frequencydomain signal through DFT, mapped to a subcarrier, IFFT-processed, andthen transmitted (refer to FIG. 4).

FIG. 7 shows a symbol position to which an RS is mapped in a subframestructure according to SC-FDMA.

FIG. 7( a) shows an RS located at the fourth SC-FDMA symbol in each oftwo slots in one subframe in the case of normal CP. FIG. 7( b) shows anRS located at the third SC-FDMA symbol of each of two slots in onesubframe in the case of extended CP.

FIG. 8 illustrates a signal processing procedure of mapping DFT processoutput samples to a single carrier in clustered SC-FDMA and FIGS. 9 and10 illustrate a signal processing procedure of mapping DFT processoutput samples to multiple carriers in clustered SC-FDMA.

FIG. 8 shows an example to which intra-carrier clustered SC-FDMA isapplied and FIGS. 9 and 10 show an example to which inter-carrierclustered SC-FDMA is applied. FIG. 9 shows a case in which a signal isgenerated through a single IFFT block when subcarrier spacing betweenneighboring component carriers is aligned and component carriers arecontiguously allocated in the frequency domain. FIG. 10 shows a case inwhich a signal is generated through a plurality of IFFT blocks whencomponent carriers are non-contiguously allocated in the frequencydomain.

FIG. 11 illustrates a signal processing procedure of segmented SC-FDMA.

Segmented SC-FDMA employs as many IFFTs as the number of DFTs such thatDFT and IFFT has one-to-one relationship to extend DFT spread andfrequency subcarrier mapping of IFFT of SC-FDMA and may be referred toas NxSC-FDMA or NxDFT-s-OFDMA. The term segmented SC-FDMA is used in thespecification. Referring to FIG. 11, the segmented SC-FDMA groups timedomain modulation symbols into N (N being an integer greater than 1)groups and performs a DFT process group by group in order to relieve thesingle carrier property condition.

FIG. 12 shows a structure of an uplink subframe that can be used inembodiments of the present invention.

Referring to FIG. 12, the uplink subframe includes a plurality of slots(e.g. two slots). The number of SC-FDMA symbols included in each slotmay depend on CP length. For example, a slot can include 7 SC-FDMAsymbols in the case of normal CP.

The uplink subframe is segmented into a data region and a controlregion. The data region, which is for transmitting and receiving a PUSCHsignal, is used to transmit an uplink data signal such as audio data.The control region, which is for transmitting and receiving a PUCCHsignal, is used to transmit UCI.

PUCCH includes RB pairs (e.g. m=0, 1, 2, 3) located at both ends of thedata region (e.g. RB pairs located at frequency mirrored portions) inthe frequency domain and hopped on the basis of a slot. UCI includesHARQ ACK/NACK, channel quality information (CQI), precoding matrixindicator (PMI), rank indication (RI) information, etc.

FIG. 13 illustrates a procedure of processing UL-SCH data and controlinformation which can be used in the embodiments of the presentinvention.

Referring to FIG. 13, data transmitted through an UL-SCH is delivered inthe form of a transport block (TB) to a coding unit for eachtransmission time interval (TTI).

Parity bits p₀, p₁, p₂, p₃, . . . , p_(L-1) are added to bits a₀, a₁,a₂, a₃, . . . , a_(A-1) of a TB received from a higher layer. Here, thesize of the TB is A and the number of the parity bits is 24 (L=24).Input bits having a CRC attached thereto may be represented as b₀, b₁,b₂, b₃, . . . , b_(B-1) where B denotes the number of bits of the TBincluding the CRC (S1300).

The input bits b₀, b₁, b₂, b₃, . . . , b_(B-1) are segmented into codeblocks (CBs) according to the TB size and a CRC is attached to each ofthe segmented CBs to obtain bits c_(r0), c_(r1), c_(r2), c_(r3), . . . ,c_(r(K) _(r) ₋₁₎. Here, r denotes a CB number (r=0, . . . , C−1), K_(r)denotes the number of bits of a CB r, and C represents the total numberof CBs (s1310).

Channel coding is performed on c_(r0), c_(r1), c_(r2), c_(r3), . . . ,c_(r(K) _(r) ₋₁₎ input to a channel coding unit to generate d_(r0)^((i)), d_(r1) ^((i)), d_(r2) ^((i)), d_(r3) ^((i)), . . . , d_(r(D)_(r) ₋₁₎ ^((i)). Here, i (i=0, 1, 2) denotes an index of a coded datastream, denotes the number of bits of an i-th coded data stream, D_(r)for the code block r (that is, D_(r)=K_(r)+4), r represents CB number,and C represents the total number of CBs. In the embodiments of thepresent invention, each CB can be channel-coded using turbo-coding(S1320).

Upon completion of the channel coding, rate matching is performed togenerate e_(r0), e_(r1), e_(r2), e_(r3), . . . , e_(r(E) _(r) ₋₁₎. Here,denotes the number of rate-matched bits of an r-th CB (r=0, 1, . . . ,C−1), and C denotes the total number of CBs (S1330).

After rate matching, CB concatenation is performed to result in bits f₀,f₁, f₂, f₃, . . . , f_(G-1). Here, G represents the total number ofcoded bits. When the control information is multiplexed with the UL-SCHdata and transmitted, bits used to transmit the control information arenot included in G. Bits f₀, f₁, f₂, f₃, . . . , f_(G-1) correspond to aUL-SCH codeword (S1340).

CQI and/or PMI, RI and HARQ-ACK of the UCI are independentlychannel-coded (s1350, 51360 and S1370). Channel coding of UCI isperformed on the basis of the number of coded symbols for UCI. Forexample, the number of coded symbols can be used for rate matching ofcoded control information. The number of coded symbols corresponds tothe number of modulation symbols and the number of REs.

The CQI is channel-coded using an input bit sequence o₀, o₁, o₂, . . . ,o_(O-1) (S1350) to result in an output bit sequence q₀, q₁, q₂, q₃, . .. , q_(Q) _(CQI) ₋₁. A channel coding scheme for the CQI depends on thenumber of bits of the CQI. When the CQI has 11 bits or more, an 8-bitCRC is added to the CQI. In the output bit sequence, Q_(CQI) denotes thetotal number of coded bits for the CQI. The coded CQI can berate-matched in order to match the length of the bit sequence toQ_(CQI). Q_(CQI)=Q′_(CQI)×Q_(m) where Q′_(CQI) is the number of codedsymbols for the CQI and Q_(m) is the modulation order. Q_(m) of the CQIis equal to that of the UL-SCH data.

The RI is channel-coded using an input bit sequence [o₀ ^(RI)] Or [o₀^(RI) o₁ ^(RI)] (S1360). Here, [o₀ ^(RI)] and [o₀ ^(RI) o₁ ^(RI)] denote1-bit RI and 2-bit RI, respectively.

In the case of 1-bit RI, repetition coding is used. For the 2-bit RI,(3,2) simplex code is used for coding and encoded data can be cyclicallyrepeated. RI having 3 to 11 bits is coded using (32,0) RM code used inan uplink shared channel. RI having 12 bits or more is divided into twogroups using a double RM structure and each group is coded using the(32,0) RM code. An output bit sequence q₀ ^(RI), q₁ ^(RI), q₂ ^(RI), . .. , q_(Q) _(RI) ⁻¹ ^(RI) is obtained by concatenating coded RI blocks.Here, Q_(RI) represents the total number of coded bits for the RI. Thecoded RI block finally concatenated may be part of the RI in order tomatch the length of the coded RI to Q_(RI) (that is, rate matching).Q_(RI)=Q′_(RI)×Q_(m) where Q′_(RI) is the number of coded symbols forthe RI and Q_(m) is the modulation order. Q_(m) of the RI is equal tothat of the UL-SCH data.

HARQ-ACK is channel-coded using an input bit sequence [o₀ ^(ACK)], [o₀^(ACK) o₁ ^(ACK)] or [o₀ ^(ACK) o₁ ^(ACK) . . . o_(O) _(ACK) ⁻¹^(ACK)](S1370). [o₀ ^(ACK)] and [o₀ ^(ACK) o₁ ^(ACK)] respectively mean1-bit HARQ-ACK and 2-bit HARQ-ACK. [o₀ ^(ACK) o₁ ^(ACK) . . . o_(O)_(ACK) ⁻¹ ^(ACK)] represents HARQ-ACK composed of information of morethan two bits (that is, O^(ACK)>2).

At this time, ACK is coded into 1 and NACK is coded into 0. 1-bitHARQ-ACK is coded using repetition coding. 2-bit HARQ-ACK is coded usinga (3,2) simplex code and encoded data can be cyclically repeated.HARQ-ACK having 3 to 11 bits is coded using a (32,0) RM code used in anuplink shared channel. HARQ-ACK of 12 bits or more is divided into twogroups using a double RM structure and each group is coded using a(32,0) RM code. Q_(ACK) denotes the total number of coded bits for theHARQ-ACK and a bit sequence q₀ ^(ACK), q₁ ^(ACK), q₂ ^(ACK), . . . ,q_(Q) _(ACK) ⁻¹ ^(ACK) is obtained by concatenating coded HARQ-ACKblocks. The coded HARQ-ACK block finally concatenated may be part of theHARQ-ACK in order to match the length of the bit sequence to Q_(ACK)(that is, rate matching). Q_(ACK)=Q′_(ACK)×Q_(m) where Q′_(ACK) is thenumber of coded symbols for the HARQ-ACK and Q_(m) is the modulationorder. Q_(m) of the HARQ-ACK is equal to that of the UL-SCH data.

Coded UL-SCH bits f₀, f₁, f₂, f₃, . . . , f_(G-1) and coded CQI/PMI bitsq₀, q₁, q₂, q₃, . . . , q_(Q) _(CQI) ⁻¹ are input to a data/controlmultiplexing block (S1380). The data/control multiplexing block outputsg ₀, g ₁, g ₂, g ₃, . . . , g _(H′−1). Here, g _(i) is a column vectorhaving a length of Q_(m) (i=0, . . . , H′−1). g _(i) (i=0, . . . , H′−1)represents a column vector having a length of (Q_(m)·N_(L)).H=(G+N_(L)·Q_(CQI)) and H′=H/(N_(L)·Q_(m)). N_(L) denotes the number oflayers to which the UL-SCH TB is mapped and H denotes the total numberof coded bits allocated to the N_(L) transport layers to which theUL-SCH TB is mapped for the UL-SCH data and CQI/PMI. That is, H is thetotal number of coded bits allocated for the UL-SCH data and CQI/PMI.

A channel interleaver channel-interleaves coded bits input thereto. Theinput of the channel interleaver includes the output of the data/controlmultiplexing block, g ₀, g ₁, g ₂, . . . , g _(H′−1), the coded RI q ₀^(RI), q ₁ ^(RI), q ₂ ^(RI), . . . , q _(Q′) _(RI) ⁻¹ ^(RI), and thecoded HARQ-ACK q ₀ ^(ACK), q ₁ ^(ACK), q ₂ ^(ACK), . . . , q _(Q′)_(ACK) ⁻¹ ^(ACK) (S1390).

In step S1390, g _(i) (i=0, . . . , H′−1) is the column vector having alength of Q_(m) for the CQI/PMI, q _(i) ^(ACK) (i=0, . . . , Q′_(ACK)−1)is a column vector of a length of Q_(m) for the ACK/NACK, and q _(i)^(RI) (Q′_(RI)=Q_(RI)/Q_(m)) is a column vector having a length of Q_(m)for the RI.

The channel interleaver multiplexes the control information and/or theUL-SCH data for PUSCH transmission. Specifically, the channelinterleaver maps the control information and the UL-SCH data to achannel interleaver matrix corresponding to the PUSCH resource.

Upon completion of channel interleaving, a bit sequence h₀, h₁, h₂, . .. , h_(H+Q) _(RI) ⁻¹ is output column by column from the channelinterleaver matrix. The output bit sequence h₀, h₁, h₂, . . . , h_(H+Q)_(RI) ⁻¹is mapped onto a resource grid.

FIG. 14 illustrates an exemplary method of multiplexing UCI and UL-SCHdata on a PUSCH.

When a UE attempts to transmit control information in a subframeassigned for PUSCH transmission, the UE multiplexes the UCI and UL-SCHdata prior to DFT-spreading. The UCI includes at least one of CQI/PMI,HARQ-ACK/NACK and RI.

The numbers of REs used to transmit the CQI/PMI, HARQ-ACK/NACK and RIare based on a modulation and coding scheme (MCS) and offset valuesΔ_(offset) ^(CQI), Δ_(offset) ^(HARQ-ACK), and Δ_(offset) ^(RI)allocated for PUSCH transmission. The offset values permit differentcoding rates according to control information and are semi-staticallyset by a higher layer (e.g. RRC layer) signal. The UL-SCH data andcontrol information are not mapped to the same RE. The controlinformation is mapped such that it is present in two slots of asubframe, as shown in FIG. 14. A BS can easily demultiplex the controlinformation and data packet since it can be aware of transmission of thecontrol information through the PUSCH in advance.

Referring to FIG. 14, CQI and/or PMI (CQI/PMI) resources are located atthe beginning of a UL-SCH data resource, sequentially mapped to allSC-FDMA symbols on one subcarrier and then mapped to the nextsubcarrier. The CQI/PMI are mapped from the left to the right insubcarriers, that is, in a direction in which the SC-FDMA symbol indexincreases. PUSCH data (UL-SCH data) is rate-matched in consideration ofthe quantity of the CQI/PMI resources (i.e., the number of codedsymbols). The CQI/PMI uses the same modulation order as that of theUL-SCH data.

For example, when the CQI/PMI has a small information size (payloadsize) (e.g. less than 11 bits), (32, k) block code is used for theCQI/PMI, similarly to PUCCH data transmission, and coded data can becyclically repeated. For CQI/PMI having a small information size, a CRCis not used.

If the CQI/PMI has a large information size (e.g. greater than 11 bits),an 8-bit CRC is added to the CQI/PMI and channel coding and ratematching are performed using a tail-biting convolutional code. TheACK/NACK is inserted into part of SC-FDMA resources to which the UL-SCHdata is mapped through puncturing. The ACK/NACK is located next to an RSand filled in corresponding SC-FDMA symbols from the bottom to the top,that is, in a direction in which the subcarrier index increases.

In the case of normal CP, SC-FDMA symbols for ACK/NACK correspond toSC-FDMA symbols #2 and #4 in each slot, as shown in FIG. 14. The codedRI is located next to symbols (i.e., symbols #1 and #5) for the ACK/NACKirrespective of whether the ACK/NACK is practically transmitted in thesubframe. Here, the ACK/NACK, RI and CQI/PMI are independently coded.

FIG. 15 is a flowchart illustrating a procedure of multiplexing controlinformation and UL-SCH data in a MIMO system.

Referring to FIG. 15, a UE identifies a rank n_sch for a UL-SCH (datapart) and PMI related to the rank from scheduling information for PUSCHtransmission (S1510). The UE determines a rank n_ctrl for UCI (S1520).The rank of the UCI can be set such that it is equal to that of theUL-SCH (n_ctrl=n_sch). However, the present invention is not limitedthereto. The data and control channel are multiplexed (S1530). A channelinterleaver performs time-first-mapping and punctures regions around aDM-RS to map ACK/NACK/RI (S1540). Then, the data and control channel aremodulated according to an MCS table (S1540). The modulation scheme mayinclude QPSK, 16QAM, and 64QAM, for example. The order/position of themodulation may be changed (e.g. before multiplexing of the data andcontrol channel).

FIGS. 16 and 17 illustrate an exemplary method for multiplexing andtransmitting a plurality of UL-SCH TBs and UCI by a UE according to anembodiment of the present invention.

While FIGS. 16 and 17 illustrate a case in which two codewords aretransmitted for convenience, the method shown in FIGS. 16 and 17 can beapplied to transmission of one or three or more codewords. A codewordand a TB correspond to each other and are used interchangeably in thespecification. Since a basic procedure of the method isidentical/similar to the procedure described above with reference toFIGS. 13 and 14, a description will be given of part related to MIMO.

Assuming that two codewords are transmitted in FIG. 16, channel codingis performed on each codeword (160). Rate matching is carried outaccording to a given MCS level and resource size (161). Encoded bits maybe cell-specifically, UE-specifically or codeword-specifically scrambled(162). Then, codeword-to-layer mapping is performed (163). Thecodeword-to-layer mapping may include layer shifting or permutation.

The codeword-to-layer mapping performed in the functional block 163 mayuse a codeword-to-layer mapping method shown in FIG. 17. The position ofprecoding performed in FIG. 17 may be different from the position ofprecoding in FIG. 13.

Referring back to FIG. 16, the control information such as CQI, RI andACK/NACK is channel-coded in a channel coding block (165) according topredetermined specifications. Here, the CQI, RI and ACK/NACK can becoded using the same channel code for all the codewords or coded usingdifferent channels codes specific to the codewords.

The number of the encoded bits may be changed by a bit side controller166. The bit size controller 166 may be unified with the channel codingblock 165. A signal output from the bit size controller 166 is scrambled(167). The scrambling can be performed cell-specifically,layer-specifically, codeword-specifically or UE-specifically.

The bit size controller 166 can operate as follows.

(1) The bit size controller recognizes a rank n_rank_pusch of data for aPUSCH.

(2) A rank n_rank_control of a control channel is set to correspond tothe rank of the data (i.e., n_rank_control=n_rank_pusch) and the numberof bits (n_bit_ctrl) for the control channel is extended by multiplyingit by the rank of the control channel.

This is performed by simply copying the control channel to repeat thecontrol channel. At this time, the control channel may be an informationlevel prior to channel coding or an encoded bit level after channelcoding. In the case of a control channel [a0, a1, a2, a3] havingn_bit_ctrl=4 and a data rank of n_rank_pusch=2, for example, theextended number of bits (n_ext_ctrl) of the control channel can be 8bits [a0, a1, a2, a3, a0, a1, a2, a3].

Alternatively, a circular buffer scheme may be applied such that theextended number of bits (n_ext_ctrl) becomes 8 bits.

When the bit size controller 166 and channel encoder 165 are unified,encoded bits can be generated using channel coding and rate matchingdefined in the existing system (e.g. LTE Rel-8).

In addition to the bit size controller 166, bit level interleaving maybe performed to further randomize layers. Equivalently, interleaving maybe carried out at the modulation symbol level.

CQI/PMI channels and control information (or control data) with respectto the two codewords can be multiplexed by a data/control multiplexer164. Then, a channel interleaver 168 maps the CQI/PMI according to thetime-first-mapping scheme such that ACK/NACK information is mapped toREs around an uplink DM-RS in each of two slots in one subframe.

A modulation mapper 169 modulates each layer and a DFT precoder 170performs DFT precoding. A MIMO precoder 171 carries out MIMO precodingand a resource element mapper 172 sequentially executes RE mapping.Then, an SC-FDMA signal generator 173 generates an SC-FDMA signal andtransmits the generated signal through an antenna port.

The positions of the aforementioned functional blocks are not limited tolocations shown in FIG. 16 and can be changed. For example, thescrambling blocks 162 and 167 can follow the channel interleaving block168 and the codeword-to-layer mapping block 163 can follow the channelinterleaving block 168 or the modulation mapper 169.

2. Multi-carrier Aggregation Environment

Communication environments considered in the embodiments of the presentinvention include multi-carrier environments. A multi-carrier system ora carrier aggregation system used in the present invention means asystem that uses aggregation of one or more component carriers (CCs)having bandwidths narrower than a target bandwidth to supportbroad-band.

Multi-carrier means carrier aggregation (carrier concatenation in thepresent invention. The carrier aggregation includes concatenation ofnon-contiguous carriers as well as concatenation of contiguous carriers.Furthermore, carrier concatenation can be used interchangeably with theterms “carrier aggregation”, “bandwidth concatenation”, etc.

Multi-carrier (i.e. carrier aggregation) composed of two or more CCsaims to support up to 100 MHz in the LTE-A system. When one or morecarriers having bandwidths narrower than a target bandwidth areaggregated, the bandwidths of the aggregated carriers can be limited tothe bandwidth used in the existing system in order to maintain backwardscompatibility with the existing IMT system.

For example, the 3GPP LTE system supports {1, 4, 3, 5, 10, 15, 20}MHzand the 3GPP LTE-Advanced system (LTE-A) supports bandwidths wider than20 MHz using the bandwidths supported by LTE. The multi-carrier systemused in the present invention can define a new bandwidth irrespective ofthe bandwidths used in the existing systems to support carrieraggregation.

The LTE-A system uses the concept of the cell to manage radio resources.The cell is defined as a combination of downlink resources and uplinkresources. The uplink resources are not an essential element, and thusthe cell may be composed of downlink resources only. If multi-carrier(i.e. carrier aggregation) is supported, linkage between a carrierfrequency (or DL CC) of the downlink resource and a carrier frequency(or UL CC) of the uplink resource can be indicated by system information(SIB).

Cells used in the LTE-A system include a primary cell (P cell) and asecondary cell (S cell). The P cell may mean a cell operating at aprimary frequency (e.g., primary CC (PCC)) and the S cell may mean acell operating at a secondary frequency (e.g., secondary CC (SCC)). Fora specific UE, only one P cell and one or more S cells can be allocated.

The P cell is used for a UE to perform an initial connectionestablishment procedure or a connection re-establishment procedure. TheP cell may mean a cell designated during a handover procedure. The Scell can be configured after RRC connection is established and used toprovide additional radio resources.

The P cell and the S cell can be used as serving cells. For a UE forwhich carrier aggregation is not set although the UE is in anRRC-connected state or a UE which does not support carrier aggregation,only one serving cell configured with only the P cell is present. In thecase of a UE in an RRC-connected state, for which carrier aggregation isset, one or more serving cells can be present and the serving cellsinclude the P cell and one or more S cells.

Upon beginning an initial security activation procedure, an E-UTRAN canestablish a network including one or more S cells in addition to the Pcell initially configured in a connection establishment procedure. In amulti-carrier environment, the P cell and S cell can operate ascomponent carriers. That is, carrier aggregation can be understood as acombination of the P cell and one or more S cells. In the followingembodiments, the PCC corresponds to the P cell and the SCC correspondsto the S cell.

3. Uplink Control Information Transmission Method

The embodiments of the present invention relate to a method forchannel-coding UCI, a method for allocating resources to the UCI and amethod for transmitting the UCI when the UCI piggybacks on data on aPUSCH in a CA environment. The embodiments of the present invention canbe applied to SU-MIMO and, especially, to a single-antenna transmissionenvironment as a special case of SU-MIMO.

3.1 UCI Allocation Position on PUSCH

FIG. 18 illustrates an exemplary method for mapping physical resourceelements in order to transmit uplink data and UCI.

FIG. 18 shows a UCI transmission method in the case of 2 codewords and 4layers. Referring to FIG. 18, CQI is combined with data and mapped toREs other than REs to which RI is mapped through the time-first-mappingscheme using the same modulation order as the data and all constellationpoints. In SU-MIMO, the CQI is spread in one codeword to be transmitted.For example, the CQI is transmitted in a codeword having a higher MCSlevel among the two codewords and transmitted in codeword 0 when the twocodewords have the same MCS level.

ACK/NACK is arranged while puncturing combinations of the CQI and data,which have been mapped to symbols located on both sides of referencesignals. Since the reference signals are located at third and tenthsymbols, the ACK/NACK is mapped from the lowest subcarriers of second,fourth, ninth and eleventh symbols to the top. Here, ACK/NACK is mappedin the order of the second, eleventh, ninth and fourth symbols.

RI is mapped to symbols located next to the ACK/NACK. The RI is thefirst to be mapped among all information items (data, CQI, ACK/NACK, RI)transmitted on the PUSCH. Specifically, the RI is mapped from the lowestsubcarriers of first, fifth, eighth and twelfth symbols to the top.Here, the RI is mapped in the order of the first, twelfth, eighth andfifth symbols.

Particularly, the ACK/NACK and RI can be mapped using only four cornersof constellation through QPSK when their information bits are 1 bit or 2bits and mapped using the same modulation order as the data and allconstellation points when their information bits are 3 bits or more. Inaddition, the ACK/NACK and RI transmit the same information using thesame resource at the same position in all layers.

3.2 Calculation of the Number of Coded Modulation Symbols for HARQ-ACKBits or RI−1

In the embodiments of the present invention, the number of modulationsymbols may correspond to the number of coded symbols or the number ofREs.

Control information or control data is input to the channel coding block(e.g., S1350, S1360 and S1370 of FIG. 13 or 165 of FIG. 16) in the formof channel quality control information (CQI and/or PMI), HARQ/ACK andRI. Different numbers of encoded symbols are allocated for controlinformation transmission, and thus coding rate depends on the controlinformation. When the control information is transmitted in a PUSCH,control information bits o₀, o₁, o₂, . . . , o_(o-1) of HARQ-ACK, RI andCQI (or PMI) which are uplink channel state information (CSI) areindependently channel-coded.

When a UE transmits ACK/NACK (or RI) information bits though a PUSCH,the number of REs per layer for the ACK/NACK (or RI) can be calculatedby Equation 1.

$\begin{matrix}{Q^{\prime} = {\min{\quad\left( {\left\lceil \frac{O \cdot M_{sc}^{{PUSCH} - {initial}} \cdot N_{symb}^{{PUSCH} - {initial}} \cdot \beta_{offset}^{PUSCH}}{{\sum\limits_{r = 0}^{C^{(0)} - 1}K_{r}^{(0)}} + {\sum\limits_{r = 0}^{C^{(1)} - 1}K_{r}^{(1)}}} \right\rceil,{4 \cdot M_{sc}^{PUSCH}}} \right)}}} & \left\lbrack {{Equation}\mspace{14mu} 1} \right\rbrack\end{matrix}$

In Equation 1, the number of REs for the ACK/NACK (or RI) can berepresented as the number of coded modulation symbols, Q′. Here, Orepresents the number of bits of the ACK/NACK (or RI), and β_(offset)^(HARQ-ACK) and β_(offset) ^(RI) are determined by the number oftransmission codewords according to TB. Parameters for setting an offsetvalue for considering an SNR difference between data and UCI aredetermined as β_(offset) ^(PUSCH)=β_(offset) ^(HARQ-ACK) and β_(offset)^(PUSCH)=β_(offset) ^(RI).

M_(sc) ^(PUSCH) represents a scheduled bandwidth for PUSCH transmissionin the current subframe for a TB, as the number of subcarriers. N_(symb)^(PUSCH-initial) represents the number of SC-FDMA symbols per subframefor initial PUSCH transmission for the same TB, and N_(sc)^(PUSCH-initial) represents the number of subcarriers per subframe forinitial PUSCH transmission. N_(symb) ^(PUSCH-initial) can be calculatedby Equation 2.N _(symb) ^(PUSCH-initial)=(2·(N _(symb) ^(UL)−1)−N _(SRS))  [Equation2]

Here, N_(SRS) can be set to 1 when the UE transmits the PUSCH and SRS inthe same subframe for initial transmission or when PUSCH resourceallocation for the initial transmission even partially overlaps with thesubframe and frequency bandwidth of a cell-specific SRS, and set to 0otherwise.

The number of subcarriers of the TB for initial transmission, M_(sc)^(PUSCH-initial), the total number of code blocks derived from the TB,C, and the size of each code block, K_(r) ^((x)) (x={0,1}), can beobtained from the initial PDCCH for the same TB.

When the initial PDCCH (DCI format 0 or 4) does not include the abovevalues, these values can be determined by other methods. For example,M_(sc) ^(PUSCH-initial), C and K_(r) ^((x)) (x={0,1}) can be determinedfrom the latest semi-persistently scheduled PDCCH when the initial PUSCHfor the same TB is semi-persistently scheduled. Otherwise, when thePUSCH is initiated according to a random access response grant, thevalues can be determined from a random access response grant for thesame TB.

When the number of REs for ACK/NACK (or RI) has been obtained asdescribed above, the number of bits can be calculated in considerationof a modulation scheme after channel coding of the ACK/NACK (or RI). Thetotal number of coded bits of the ACK/NACK is Q_(ACK)=Q_(m)·Q′ and thetotal number of coded bits of the RI is Q_(RI)=Q_(m)·Q′. Here, Q_(m) isthe number of bits per symbol according to modulation order andcorresponds to 2 in the case of QPSK, 4 in the case of 16QAM, and 6 inthe case of 64QAM.

When SNR or spectral efficiency is high, a minimum value of REsallocated to the ACK/NACK and RI can be determined in order to preventrate matching from acting as puncturing to make a minimum length of acodeword coded with Reed-Muller (RM) code zero. At this time, theminimum value of the REs may depend on the information bit size of theACK/NACK or RI.

3.3 Calculation of the Number of Coded Modulation Symbols for CQI and/orPMI−1

When a UE transmits CQI and/or PMI (CQI/PMI) bits over a PUSCH, thenumber of REs for the CQI/PMI per layer can be calculated by Equation 3.

$\begin{matrix}{Q^{\prime} = {\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {initial}} \cdot N_{symb}^{{PUSCH} - {initial}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}}{Q_{m}}}} \right)}} & \left\lbrack {{Equation}\mspace{14mu} 3} \right\rbrack\end{matrix}$

In Equation 3, the number of REs for the CQI and/or PMI can berepresented as the number of modulation coded symbols, Q′ for channelquality information. While the following description will mainly focuson CQI, the present invention can be applied to PMI in the same manner.

In Equation 3, O represents the number of bits of the CQI/PMI and Lrepresents the number of bits of a CRC attached to the CQI bits. Here, Lis 0 when O is 11 bits or less and is 8 otherwise. That is,

$L = \left\{ \begin{matrix}0 & {O \leq 11} \\8 & {{otherwise}.}\end{matrix} \right.$

β_(offset) ^(CQI) is determined by the number of transport codewords forthe corresponding PUSCH and a parameter for determining an offset valuefor considering an SNR difference between data and UCI is determined asβ_(offset) ^(PUSCH)=β_(offset) ^(CQI).

M_(sc) ^(PUSCH) represents a scheduled bandwidth for PUSCH transmissionin the current subframe for the TB, as the number of subcarriers.N_(symb) ^(PUSCH) denotes the number of SC-FDMA symbols in the currentsubframe transmitting the PUSCH and can be calculated by theaforementioned Equation 2.

N_(symb) ^(PUSCH-initial) represents the number of SC-FDMA symbols perinitial PUSCH transmission subframe for the same TB and M_(sc)^(PUSCH-initial) denotes the number of subcarriers for the correspondingsubframe. For K_(r) ^((x)), x indicates the index of a TB having ahighest MCS, designated by an uplink grant.

M_(sc) ^(PUSCH-initial), C and K_(r) ^((x)) can be acquired from theinitial PDCCH for the same TB. When M_(sc) ^(PUSCH-initial), C and K_(r)^((x)) are not included in the initial PDCCH (DCI format 0), the UE candetermine these values using other methods.

For example, M_(sc) ^(PUSCH-initial), C and K_(r) ^((x)); can bedetermined from the latest semi-persistently scheduled PDCCH when theinitial PUSCH for the same TB is semi-persistently scheduled. Otherwise,when the PUSCH is initiated according to a random access response grant,M_(sc) ^(PUSCH-initial), C and K_(r) ^((x)) can be determined from arandom access response grant for the same TB.

Data information (G) bits of UL-SCH can be calculated by Equation 4.G=N _(symb) ^(PUSCH) ·M _(sc) ^(PUSCH) ·Q _(m) −Q _(CQI) −Q_(RI)  [Equation 4]

When the number of REs for the CQI has been obtained as described above,the number of bits can be calculated in consideration of a modulationscheme after channel coding of the CQI. Q_(CQI) is the total number ofcoded bits of the CQI and Q_(CQI)=Q_(m)·Q′. Here, Q_(m) is the number ofbits per symbol according to modulation order and corresponds to 2 inthe case of QPSK, 4 in the case of 16QAM, and 6 in the case of 64QAM. IfRI is not transmitted, R_(RI)=0.

3.4 Calculation of the Number of Coded Modulation Symbols for HARQ-ACKBits or RI−2

A description will be given of methods for calculating the number of REsused for ACK/NACK and RI, which are different from the methods describedin paragraph 3.1.

When a UE transmits HARQ-ACK bits or RI bits in a single cell, the UEneeds to determine the number of coded modulation symbols per layer forthe HARQ-ACK or RI, Q′. The following Equation 5 is used to calculatethe number of modulation symbols when only one TB is transmitted in anUL cell.

$\begin{matrix}{Q^{\prime} = {\min\left( {\left\lceil \frac{O \cdot M_{sc}^{{PUSCH} - {initial}} \cdot N_{symb}^{{PUSCH} - {initial}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C - 1}K_{r}} \right\rceil,{4 \cdot M_{sc}^{PUSCH}}} \right)}} & \left\lbrack {{Equation}\mspace{14mu} 5} \right\rbrack\end{matrix}$

In Equation 5, the number of REs for the ACK/NACK (or RI) can berepresented as the number of coded modulation symbols, Q′. Here, Odenotes the number of bits of the ACK/NACK (or RI).

β_(offset) ^(HARQ-ACK) and β_(offset) ^(RI) are determined by the numberof transmission codewords according to TB. Parameters for setting anoffset value for considering an SNR difference between data and UCI aredetermined as β_(offset) ^(PUSCH)=β_(offset) ^(HARQ-ACK) and β_(offset)^(PUSCH)=β_(offset) ^(RI).

M_(sc) ^(PUSCH) represents a bandwidth, which is allocated (scheduled)for PUSCH transmission in the current subframe for a TB, as the numberof subcarriers. N_(symb) ^(PUSCH-initial) denotes the number of SC-FDMAsymbols per initial PUSCH transport subframe for the same TB and M_(sc)^(PUSCH-initial) represents the number of subcarriers per subframe forinitial PUSCH transmission. N_(symb) ^(PUSCH-initial) can be calculatedby Equation 2.

The number of subcarriers of the TB for initial transmission, M_(sc)^(PUSCH-initial), the total number of code blocks derived from the TB,C, and the size of each code block, K_(r) ^((x)) (x={0,1}), can beobtained from the initial PDCCH for the same TB.

When the initial PDCCH (DCI format 0 or 4) does not include the abovevalues, these values can be determined by other methods. For example,N_(sc) ^(PUSCH-initial), C and K_(r) ^((x)) (x={0,1}) can be determinedfrom the latest semi-persistently scheduled PDCCH when the initial PUSCHfor the same TB is semi-persistently scheduled. Otherwise, when thePUSCH is initiated according to a random access response grant, thevalues can be determined from a random access response grant for thesame TB.

When the UE transmits two TBs in the UL cell, the UE needs to determinethe number of coded modulation symbols per layer for the HARQ-ACK or RI,Q′. The following Equations 6 and 7 are used to calculate the number ofmodulation symbols when two TBs have different initial transmissionresource values in the UL cell.

$\begin{matrix}{\mspace{79mu}{Q^{\prime} = {\max\left\lbrack {{\min\left( {Q_{temp}^{\prime},{4 \cdot M_{sc}^{PUSCH}}} \right)},Q_{\min}^{\prime}} \right\rbrack}}} & \left\lbrack {{Equation}\mspace{14mu} 6} \right\rbrack \\{Q_{{temp} =}^{\prime}\left\lceil \frac{O \cdot M_{sc}^{{PUSCH} - {{initial}{(1)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(1)}}} \cdot M_{sc}^{{PUSCH} - {{initial}{(2)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(2)}}} \cdot \beta_{offset}^{PUSCH}}{{\sum\limits_{r = 0}^{C^{(1)} - 1}{K_{r}^{(1)} \cdot M_{sc}^{{PUSCH} - {{initial}{(2)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(2)}}}}} + {\sum\limits_{r = 0}^{C^{(2)} - 1}{K_{r}^{(2)} \cdot M_{sc}^{{PUSCH} - {{initial}{(1)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(1)}}}}}} \right\rceil} & \left\lbrack {{Equation}\mspace{14mu} 7} \right\rbrack\end{matrix}$

In Equations 6 and 7, the number of REs for the ACK/NACK (or RI) can berepresented by the number of coded modulation symbols, Q′. Here, Odenotes the number of bits of the ACK/NACK (or RI). Q′_(min)=O if O≦2and Q′_(min)=┌2O/Q′_(m)┐ and Q′_(m)=min(Q_(m) ¹,Q_(m) ²) otherwise.Q_(m) ^(x) (x={1,2}) represents the modulation order of TB ‘x’ andM_(sc) ^(PUSCH-initial) (x={1,2}) denotes a scheduled bandwidthrepresented as the number of subcarriers for PUSCH transmission in theinitial subframe for first and second TBs.

N_(symb) ^(PUSCH-initial(x)) (x={1,2}) indicates the number of SC-FDMAsymbols per subframe for initial PUSCH transmission for the first andsecond TBs and can be calculated by Equation 8.N _(symb) ^(PUSCH-initial(x))=(2·(N _(sym) ^(UL)−1)−N _(SRS)^((x))),x={1,2}  [Equation 8]

In Equation 8, N_(SRS) ^((x)) (x=={1,2}) is 1 when the UE transmits thePUSCH and SRS in the same subframe for initial transmission of the TB‘x’ or when PUSCH resource allocation for initial transmission of the TB‘x’ partially overlaps with the subframe and bandwidth of acell-specific SRS and N_(SRS) ^((x)) (x={1,2}) is 0 otherwise.

In the embodiments of the present invention, the UE can acquire M_(sc)^(PUSCH-initial(x)) (x={1,2}), C and K_(r) ^((x)) (x={1,2}) from theinitial PDCCH for the corresponding TB. When these values are notincluded in the initial PDCCH (DCI format 0 or 4), the UE can determinethese values using other methods. For example, M_(sc)^(PUSCH-initial(x)) (x={1,2}), C and K_(r) ^((x)) (x={1,2}) can bedetermined from the latest semi-persistently scheduled PDCCH when theinitial PUSCH for the same TB is semi-persistently scheduled. Otherwise,when the PUSCH is initiated according to a random access response grant,M_(sc) ^(PUSCH-initial(x)) (x={1,2}), C and K_(r) ^((x)) (x={1,2}) canbe determined from a random access response grant for the same TB.

In Equations 6 and 7, β_(offset) ^(HARQ-ACK) and β_(offset) ^(RI) aredetermined by the number of transmission codewords according to TB.Parameters for setting an offset value for considering an SNR differencebetween data and UCI are determined as β_(offset) ^(PUSCH)=β_(offset)^(HARQ-ACK) and β_(offset) ^(PUSCH)=β_(offset) ^(RI).

3.5 Calculation of the Number of Coded Modulation Symbols for CQI and/orPMI−2

When a UE transmits CQI and/or PMI (CQI/PMI) bits over a PUSCH, the UEneeds to calculate the number of REs for the CQI/PMI per layer. Whilethe following description will mainly focus on CQI, the presentinvention can be applied to PMI in the same manner.

FIG. 19 illustrates a method for transmitting UCI according to anembodiment of the present invention.

Referring to FIG. 19, an eNB can transmit an initial PDCCH signalincluding DCI format 0 or DCI format 4 to a UE (S1910).

The initial PDCCH signal may include information about the number ofsubcarriers, M_(sc) ^(PUSCH-initial(x)), information about the number ofcode blocks, C^((x)), and information about a code block size, K_(r)^((x)) for one of two transport blocks.

If M_(sc) ^(PUSCH-initial(x)), C^((x)), and K_(r) ^((x)) are notincluded in the initial PDCCH signal (DCI format 0/4) in step S1910, theUE can determine the values using another method.

For example, M_(sc) ^(PUSCH-initial(x)), C^((x)) and K_(r) ^((x)) can bedetermined from the latest semi-persistently scheduled PDCCH when theinitial PUSCH for the same TB is semi-persistently scheduled. Otherwise,when the PUSCH is initiated according to a random access response grant,M_(sc) ^(PUSCH-initial(x)), C^((x)) and K_(r) ^((x)) can be determinedfrom a random access response grant for the same TB.

Referring back to FIG. 19, the UE can calculate REs for transmitting UCIusing the information received in step S1910. Particularly, the UE cancalculate the number of REs required to transmit CQI/PMI from among theUCI (S1920).

In the embodiments of the present invention, CQI/PMI is spread ormultiplexed in all layers belonging to a TB having a maximum MCS andtransmitted. If two TBs have the same MCS levels, CQI is transmitted inthe first of the two TBs.

However, since the two TBs may have different initial RB sizes due toretransmission, the number of REs, Q′, for the CQI transmitted throughthe PUSCH in step S1920 can be calculated by Equation 9.

$\begin{matrix}{Q^{\prime} = {\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {{initial}{(x)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(x)}}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}^{(x)}}{Q_{m}^{(x)}}}} \right)}} & \left\lbrack {{Equation}\mspace{14mu} 9} \right\rbrack\end{matrix}$

Equation 9 is similar to Equation 3. However, Equation 3 cannot be usedif TBs transmitting retransmission packets have different initial RBsizes when UL data and/or UCI are retransmitted. That is, Equation 9 canbe applied when a PUSCH is transmitted using one or more TBs in amulti-carrier aggregation environment.

In Equation 9, O represents the number of bits of the CQI and Lrepresents the number of bits of a CRC attached to the CQI bits. Here, Lis 0 when O is 11 bits or less and is 8 otherwise. That is,

$L = \left\{ \begin{matrix}0 & {O \leq 11} \\8 & {{otherwise}.}\end{matrix} \right.$

Here, β_(offset) ^(CQI) is determined by the number of transportcodewords according to TBs and a parameter for determining an offsetvalue for considering an SNR difference between data and UCI isdetermined as β_(offset) ^(PUSCH)=β_(offset) ^(CQI).

M_(sc) ^(PUSCH-initial(x)) represents the number of subcarriers for thecorresponding subframe, C^((x)) represents the total number of codeblocks generated from each of the TBs, and K_(r) ^((x)) denotes the sizeof the code block according to index r. As to K_(r) ^((x)), x representsthe transport block (TB) index corresponding to the highest MCS value(I_(MCS)), designated by an initial uplink grant.

At this time, the UE can obtain information about M_(sc)^(PUSCH-initial(x)), C^((x)), and K_(r) ^((x)) from the initial PDCCH instep S1910.

N_(symb) ^(PUSCH-initial(x)) represents the number of SC-FDMA symbolsper initial PUSCH transmission subframe for the same TB. Here, N_(symb)^(PUSCH-initial(x)) is the number of SC-FDMA symbols per subframe forinitial PUSCH transmission for first and second TBs.

In addition, the UE can calculate N_(symb) ^(PUSCH-initial(x)) usingEquation 10.N _(symb) ^(PUSCH-initial(x))=(2·(N _(symb) ^(UL)−1)−N _(SRS) ^((x)),x={1,2}  [Equation 10]

In Equation 10, N_(SRS) ^((x)) can be set to 1 when the UE transmits thePUSCH and SRS in the same subframe for initial transmission of TB ‘x’ orwhen PUSCH resource allocation for initial transmission of the TB ‘x’partially overlaps with the subframe and frequency bandwidth of acell-specific SRS and to 0 otherwise.

Referring back to Equation 9, M_(sc) ^(PUSCH) represents a scheduledbandwidth for PUSCH transmission in the current subframe for the TB, asthe number of subcarriers. N_(symb) ^(PUSCH) denotes the number ofSC-FDMA symbols in the current subframe that transmits the PUSCH.

In Equation 9, ‘x’ denotes a TB corresponding to a maximum MCS level(I_(MCS)) designated by initial UL grant. If two TBs have the same MCSlevel in the initial UL grant, x can be set to 1 which indicates thefirst of the TBs.

Referring back to FIG. 19, the UE can generate UCI (CSI) including CQIusing the number of REs, calculated in step S1920. Here, UCI other thanthe CQI can be calculated using Equations 1 and 2 and 5 to 8 (S1930).

The UE can calculate information (G) of uplink data (UL-SCH) transmittedthrough the PUSCH. That is, the UE can calculate information aboutuplink data which will be transmitted together with the UCI computed instep S1930. Then, the UE can transmit a PUSCH including the UCI and ULdata to the eNB (S1940).

In step S1940, bits of UL-SCH data information (G) can be calculated byEquation 11.G=N _(L) ^((x))·(N _(symb) ^(PUSCH) ·M _(sc) ^(PUSCH) ·Q _(m) ^((x)) −Q_(CQI) −Q _(RI) ^((x)))  [Equation 11]

When the UE has calculated the number of REs for the CQI (refer toequation 9), the UE can obtain the number of bits in consideration of amodulation scheme for the CQI after CQI channel coding. In Equation 11,N_(L) ^((x)) represents the number of layers corresponding to an x-thUL-SCH TB and Q_(CQI) represents the total number of coded bits of theCQI. Q_(CQI)=Q_(m) ^((x))·Q′. Here, Q_(m) ^((x)) is the number of bitsper symbol according to the modulation order in each TB and correspondsto 2 in the case of QPSK, 4 in the case of 16QAM, and 6 in the case of64QAM. Since uplink resources for RI are preferentially allocated, thenumber or REs allocated to the RI is excluded from the uplink datainformation (G) bits. If the RI is not transmitted, Q_(RI) ^((x))=0.

In FIG. 19, the number of REs allocated to the CQI is obtained usingparameters according to initial transmission of the TB (or CW)transmitting the CQI and a maximum value of the allocated REs isacquired by subtracting a value, obtained by dividing the number of bitsof RI, Q_(RI) ^((x)), defined in the TB (or CW) transmitting the CQI, bythe modulation order Q_(m) ^((x)) of the TB (or CW) transmitting theCQI, from the resources M_(sc) ^(PUSCH)·N_(symb) ^(PUSCH) of the currentsubframe (refer to Equation 9).

FIG. 20 illustrates a method for transmitting UCI according to anotherembodiment of the present invention.

Referring to FIG. 20, an eNB transmits a PDCCH signal to a UE in orderto allocate downlink and uplink resources (S2010).

The UE transmits uplink data and/or UCI to the eNB over a PUSCH inresponse to control information included in the PDCCH signal (S2020).

When an error is generated in the PUSCH transmitted from the UE to theeNB in step S2020, the eNB transmits a NACK signal to the UE (S2030).

When the UE retransmits the uplink data upon reception of the NACKsignal, the UE can compute resources for transmitting the uplink dataand UCI from among radio resources allocated thereto. Accordingly, theUE can calculate the number of REs required to transmit the UCI (S2040).

In step S2040, CQI is spread in all layers belonging to a TB having ahigh MCS level to be transmitted. Here, two TBs have the same MCS level,the CQI is preferably transmitted in the first TB. However, since thePUSCH signal needs to be transmitted in step S2040, the TBs may havedifferent initial RB sizes. Accordingly, the UE preferably calculatesthe number of REs required to transmit the CQI through the methodaccording to Equation 9.

When M_(sc) ^(PUSCH-initial(x)), C^((x)) and K_(r) ^((x)) are includedin the PDCCH signal in step S2010, the UE can calculate the number ofREs for transmitting the CQI using corresponding information in stepS2040. If the UE receives a PDCCH including M_(sc) ^(PUSCH-initial(x)),C^((x)) and K_(r) ^((x)) after step S2030, the UE can calculate thenumber of the REs for transmitting the CQI using the values.

Referring back to FIG. 20, the UE can generate UCI using the number ofthe REs for transmitting the CQI, obtained in step S2040. Here, the UEcan compute the numbers of REs for transmitting HARQ-ACK and/or RI usingthe methods according to Equations 6 and 7 and generate the UCI usingthe number of the REs (S2050).

In addition, the UE can calculate UL-SCH data information G for uplinkdata to be retransmitted using Equation 10. Accordingly, the UE canmultiplex (or piggyback) the UCI with (or on) the uplink data toretransmit the uplink data to the eNB (S2060).

3.6 Channel Coding

A description will be given of a method for channel-coding the UCI onthe basis of the number of REs for the UCI, calculated using theabove-described methods.

When the information bit of ACK/NACK is 1 bit, an input sequence can berepresented as [o₀ ^(ACK)] and channel coding can be performed accordingto modulation orders as shown in Table 1. Q_(m) is the number of bitsper symbols according to modulation order and corresponds to 2, 4 and 6when QPSK, 16QAM and 64QAM are used, respectively.

TABLE 1 Q_(m) Encoded HARQ-ACK 2 [o₀ ^(ACK) y] 4 [o₀ ^(ACK) y x x] 6 [o₀^(ACK) y x x x x]

When the information bit of ACK/NACK is 2 bits, an input sequence can berepresented as [o₀ ^(ACK) o₁ ^(ACK)] and channel coding can be performedaccording to modulation orders as shown in Table 2. Here, o₀ ^(ACK) isan ACK/NACK bit for codeword 0, o₁ ^(ACK) is an ACK/NACK bit forcodeword 1, and o₂ ^(ACK)=(o₀ ^(ACK)+o₁ ^(ACK))mod 2. In Tables 1 and 2,x and y denote place-holders for scrambling the ACK/NACK information inorder to maximize the Euclidean distance of modulation symbols thattransmit the ACK/NACK information.

TABLE 2 Q_(m) Encoded HARQ-ACK 2 [o₀ ^(ACK) o₁ ^(ACK) o₂ ^(ACK) o₀^(ACK) o₁ ^(ACK) o₂ ^(ACK)] 4 [o₀ ^(ACK) o₁ ^(ACK) x x o₂ ^(ACK) o₀^(ACK) x x o₁ ^(ACK) o₂ ^(ACK) x x] 6 [o₀ ^(ACK) o₁ ^(ACK) x x x x o₂^(ACK) o₀ ^(ACK) x x x x o₁ ^(ACK) o₂ ^(ACK) x x x x]

In ACK/NACK multiplexing in FDD or TDD, if the ACK/NACK is 1 bit or 2bits, a bit sequence q₀ ^(ACK), q₁ ^(ACK), q₂ ^(ACK), . . . , q_(Q)_(ACK) ⁻¹ ^(ACK) is generated according to concatenation of multiplecoded ACK/NACK blocks. In the case of ACK/NACK bundling in TDD, a bitsequence {tilde over (q)}₀ ^(ACK), {tilde over (q)}₁ ^(ACK), {tilde over(q)}₂ ^(ACK), . . . , {tilde over (q)}_(Q) _(ACK) ⁻¹ ^(ACK) is alsogenerated according to concatenation of the multiple coded ACK/NACKblocks. Here, Q_(ACK) is the total number of coded bits of all codedACK/NACK blocks. Final concatenation of coded ACK/NACK blocks may bepartially made such that the total bit sequence length corresponds toQ_(ACK).

A scrambling sequence [w₀ ^(ACK) w₁ ^(ACK) w₂ ^(ACK) w₃ ^(ACK)] can beselected from Table 3 and index i used to select the scrambling sequencecan be calculated by Equation 12.i=(N _(bundled)−1)mod 4  [Equation 12]

TABLE 3 i [w₀ ^(ACK) w₁ ^(ACK) w₂ ^(ACK) w₃ ^(ACK)] 0 [1 1 1 1] 1 [1 0 10] 2 [1 1 0 0] 3 [1 0 0 1]

Table 3 is a scrambling sequence selection table for TDD ACK/NACKbundling.

The bit sequence q₀ ^(ACK), q₁ ^(ACK), q₂ ^(ACK), . . . , q_(Q) _(ACK)₋₁ ^(ACK) is generated by setting m to 1 in the case of 1-bit ACK/NACKand by setting m to 3 in the case of 2-bit ACK/NACK. Here, an algorithmof generating the bit sequence q₀ ^(ACK), q₁ ^(ACK), q₂ ^(ACK), . . . ,q_(Q) _(ACK) ⁻¹ ^(ACK) is illustrated in Table 4.

TABLE 4    Set I ,k to 0  while i < Q_(ACK)   if {tilde over (q)}_(i)^(ACK) = y // place-holder repetition bit q_(i) ^(ACK) = ({tilde over(q)}_(i−1) ^(ACK) + w_(└k/m┘) ^(ACK))mod2 k = (k + 1)mod 4m  else   if{tilde over (q)}_(i) ^(ACK) = x // a place-holder bit q_(i) ^(ACK) ={tilde over (q)}_(i) ^(ACK)  else // coded bit q_(i) ^(ACK) = ({tildeover (q)}_(i) ^(ACK) + w_(└k/m┘) ^(ACK))mod2 k = (k + 1)mod 4m end if i= i + 1  end while

When the ACK/NACK is 2 bits or more (i.e. [o₀ ^(ACK) o₁ ^(ACK) . . .o_(O) _(ACK) ⁻¹ ^(ACK)] and O^(ACK)>2), the bit sequence q₀ ^(ACK), q₁^(ACK), q₂ ^(ACK), . . . , q_(Q) _(ACK) ⁻¹ ^(ACK) can be computed byEquation 13.

$\begin{matrix}{q_{i}^{ACK} = {\sum\limits_{n = 0}^{O^{ACK} - 1}{\left( {o_{n}^{ACK} \cdot M_{{({i\;{mod}\; 32})},n}} \right){mod}\; 2}}} & \left\lbrack {{Equation}\mspace{14mu} 13} \right\rbrack\end{matrix}$

In Equation 13, i=0, 1, 2, . . . , Q_(ACK)−1and a basic sequence M_(i,n)can refer to Table 5.2.2.6.4-1 of 3GPP TS36.212 standard document. Avector sequence output of channel coding performed on the HARQ-ACKinformation can be defined as q ₀ ^(ACK), q ₁ ^(ACK), . . . , q _(Q′)_(ACK) ⁻¹ ^(ACK). Here, Q′_(ACK)=Q_(ACK)/Q_(m).

An algorithm of generating the bit sequence q ₀ ^(ACK), q ₁ ^(ACK), . .. , q _(Q′) _(ACK) ⁻¹ ^(ACK) is illustrated in Table 5.

TABLE 5   Set i,k to 0 while i < Q_(ACK) q _(k) ^(ACK) = [q_(i) ^(ACK)...q_(i+Q) _(m) ⁻¹ ^(ACK)]^(T)  i = i + Q_(m)  k = k + 1 end while

When the RI is 1 bit, an input sequence can be represented as [o₀ ^(RI)]and channel coding can be performed according to modulation orders asshown in Table 6.

TABLE 6 Q_(m) Encoded RI 2 [o₀ ^(RI) y] 4 [o₀ ^(RI) y x x] 6 [o₀ ^(RI) yx x x x]

Q_(m) is the number of bits according to modulation order andcorresponds to 2, 4 and 6 when QPSK, 16QAM and 64QAM are used,respectively. A mapping relationship between [o₀ ^(RI)] and RI isillustrated in Table 7.

TABLE 7 o₀ ^(RI) RI 0 1 1 2

When the RI is 2 bits, an input sequence can be represented as [o₀ ^(RI)o₁ ^(RI)] and channel coding can be performed according to modulationorders as shown in Table 8. Here, o₀ ^(RI) is the most significant bit(MSB) of the 2-bit input, o₁ ^(RI) the least significant bit (LSB) ofthe 2-bit input, and o₂ ^(RI)=(o₀ ^(RI)+o₁ ^(RI))mod 2.

TABLE 8 Q_(m) Encoded RI 2 [o₀ ^(RI) o₁ ^(RI) o₂ ^(RI) o₀ ^(RI) o₁ ^(RI)o₂ ^(RI)] 4 [o₀ ^(RI) o₁ ^(RI) x x o₂ ^(RI) o₀ ^(RI) x x o₁ ^(RI) o₂^(RI) x x] 6 [o₀ ^(RI) o₁ ^(RI) x x x x o₂ ^(RI) o₀ ^(RI) x x x x o₁^(RI) o₂ ^(RI) x x x x]

Table 9 shows an exemplary mapping relationship between [o₀ ^(RI)] andRI.

TABLE 9 o₀ ^(RI) RI 0 1 1 2

In Tables 6 and 8, x and y denote place-holders for scrambling the RI inorder to maximize the Euclidean distance of modulation symbols thattransmit the RI.

A bit sequence q₀ ^(RI), q₁ ^(RI), q₂ ^(RI), . . . , q_(Q) _(RI) ₋₁^(RI) is generated according to concatenation of multiple coded RIblocks. Here, Q_(RI) is the total number of coded bits of all coded RIblocks. Last concatenation of coded RI blocks can be partially made suchthat the total bit sequence length corresponds to Q_(RI).

A vector output sequence of channel coding performed on the RI isdefined as q ₀ ^(RI), q ₁ ^(RI), . . . , q _(Q′) _(RI) ⁻¹ ^(RI). Here,Q′_(RI)=Q_(RI)/Q_(m) and the vector output sequence can be acquiredaccording to an algorithm illustrated in Table 10.

TABLE 10   Set i,k to 0 while i < Q_(RI) q _(k) ^(RI) = [q_(i) ^(RI)...q_(i+Q) _(m) ⁻¹ ^(RI)]^(T)  i = i + Q_(m)  k = k + 1 end while

If the RI (or ACK/NACK) is 3 to 11 bits, RM coding is applied thereto togenerate a 32-bit output sequence. RM-coded RI (or ACK/NACK) blocks b₀,b₁, b₂, b₃, . . . , n_(B-1) are calculated by Equation 14. In Equation14, i=0, 1, 2, . . . , B−1 and B=32.

$\begin{matrix}{b_{i} = {\sum\limits_{n = 0}^{I - 1}{\left( {o_{n} \cdot M_{i,n}} \right){mod}\; 2}}} & \left\lbrack {{Equation}\mspace{14mu} 14} \right\rbrack\end{matrix}$

In Equation 14, i=0, 1, 2, . . . , Q_(RI)−1 and a basic sequence M_(i,n)can refer to Table 5.2.2.6.4-1 of 3GPP TS36.212 standard document.

4. Apparatuses for Implementing the Aforementioned Methods

FIG. 21 shows apparatuses for implementing the above-mentioned methodsdescribed with reference to FIGS. 1 to 20.

A UE can serve as a transmitter on uplink and as a receiver on downlink.An eNB can serve as a receiver on uplink and as a transmitter ondownlink.

The UE and the eNB may include transmission modules (Tx modules) 2140and 2150 and reception modules (Rx modules) 2160 and 2170 forcontrolling transmission and reception of data and/or messages andantennas 2100 and 2110 for transmitting and receiving information, dataand/or messages, respectively.

In addition, the UE and the eNB may respectively include processors 2120and 2130 for performing the above-described embodiments of the presentinvention and memories 2180 and 2190 for storing processing proceduresof the processors temporarily or continuously.

The embodiments of the present invention can be performed using theaforementioned components and functions of the UE and the eNB. Theapparatuses shown in FIG. 21 may further include the components shown inFIGS. 2, 3 and 4. The processors 2120 and 2130 preferably include thecomponents shown in FIGS. 2, 3 and 4.

The processor 2120 of the UE can monitor a search space to receive aPDCCH signal. Particularly, an LTE-A UE can receive a PDCCH signalwithout blocking PDCCH signals transmitted to other LTE UEs byperforming blind decoding on an extended CSS.

The processor 2120 of the UE can transmit UCI with a PUSCH signal to theeNB. Specifically, the processor 2120 of the UE can calculate thenumbers of REs for transmitting HARQ-ACK, CQI and RI using theabove-mentioned methods according to Equations 1 to 10, generate UCIusing the calculated numbers of REs, piggyback the UCI on uplink dataUL-SCH and transmit the uplink data with the UCI.

The transmission modules 2140 and 2150 and the reception modules 2160and 2170 included in the UE and the eNB can have packet modulation anddemodulation functions, a fast packet channel coding function, an OFDMApacket scheduling function, a TDD packet scheduling function and/or achannel multiplexing function. In addition, the UE and the eNB mayfurther include a low-power radio frequency (RF)/intermediate frequency(IF) module.

In the embodiments of the present invention can use a personal digitalassistant (PDA), a cellular phone, a personal communication service(PCS) phone, a global system for mobile (GSM) phone, a wideband CDMA(WCDMA) phone, a mobile broadband system (MBS) phone, a hand-held PC, anotebook PC, a smart phone, a multi-mode multi-band (MM-MB) terminal orthe like as the UE.

Here, the smart phone is a terminal having advantages of both a mobilecommunication terminal and a PDA. The smart phone can be a mobilecommunication terminal having scheduling and data communicationfunctions including facsimile transmission/reception, Internet access,etc. of the PDA. The MM-MB terminal means a terminal including amulti-modem chip, which can be operated in both a portable Internetsystem and a mobile communication system (e.g., CDMA 2000 system, WCDMAsystem, etc.).

The exemplary embodiments of the present invention may be achieved byvarious means, for example, hardware, firmware, software, or acombination thereof.

In a hardware configuration, the exemplary embodiments of the presentinvention may be achieved by one or more Application Specific IntegratedCircuits (ASICs), Digital Signal Processors (DSPs), Digital SignalProcessing Devices (DSPDs), Programmable Logic Devices (PLDs), FieldProgrammable Gate Arrays (FPGAs), processors, controllers,microcontrollers, microprocessors, etc.

In a firmware or software configuration, the exemplary embodiments ofthe present invention may be achieved by a module, a procedure, afunction, etc. performing the above-described functions or operations.Software code may be stored in a memory unit and executed by aprocessor. The memory unit may be located at the interior or exterior ofthe processor and may transmit and receive data to and from theprocessor via various known means.

It will be apparent to those skilled in the art that variousmodifications and variations can be made in the present inventionwithout departing from the spirit or scope of the invention. Thus, it isintended that the present invention cover the modifications andvariations of this invention provided they come within the scope of theappended claims and their equivalents.

The embodiments of the present invention may be applied to variouswireless access systems. The wireless access systems include 3GPP, 3GPP2and/or IEEE 802.xx (Institute of Electrical and Electronic Engineers802) system, etc. The embodiments of the present invention may beapplied to technical fields using the various wireless access systems inaddition to the wireless access systems.

What is claimed is:
 1. A method for transmitting channel quality controlinformation through a physical uplink shared channel (PUSCH) in awireless access system that supports hybrid automatic retransmit request(HARQ), the method performed by a user equipment (UE) and comprising:receiving a physical downlink control channel (PDCCH) signal includingan initial uplink grant; transmitting uplink data using two transportblocks based on the initial uplink grant; receiving a negativeacknowledgement (NACK) information for one of the two transport blocks;and transmitting a channel quality control information along with theone of the two transport blocks which is retransmitted according to theNACK information and a new transport block through the PUSCH to whichthe HARQ is applied, wherein a number of coded symbols, Q′, required totransmit the channel quality control information is calculated based onthe initial uplink grant, wherein the initial uplink grant includesinformation M_(sc) ^(PUSCH-initial(x)) on the number of subcarriers fora transport block for transmitting the channel quality controlinformation, information C^((x)) on a number of code blocks related tothe transport block for transmitting the channel quality controlinformation, and information K_(r) ^((x)) on the size of the codeblocks, and wherein ‘x’ denotes an index of the transport block fortransmitting the channel quality control information.
 2. The methodaccording to claim 1, wherein the number of coded symbols, Q′, iscalculated by${\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {{initial}{(x)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(x)}}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}^{(x)}}{Q_{m}^{(x)}}}} \right)},$wherein N_(symb) ^(PUSCH-initial(x)) represents a number of singlecarrier-frequency division multiple access (SC-FDMA) symbols per initialPUSCH transmission.
 3. The method according to claim 1, furthercomprising: calculating information about uplink data retransmittedthrough the one of the two transport block, wherein the informationabout the uplink data is calculated by G=N_(L) ^((x))·(N_(symb)^(PUSCH)·M_(sc) ^(PUSCH)·Q_(m) ^((x))−Q_(CQI)−Q_(RI) ^((x))).
 4. A userequipment (UE) for transmitting channel quality control informationthrough a physical uplink shared channel (PUSCH) in a wireless accesssystem that supports hybrid automatic retransmit request (HARQ), the UEcomprising: a receiver; a transmitter; and a processor configured totransmit the channel quality control information, wherein the processoris configured to: receive, via the receiver, a physical downlink controlchannel (PDCCH) signal including an initial uplink grant; transmit, viathe transmitter, uplink data using two transport blocks based on theinitial uplink grant; receive, via the receiver, a negativeacknowledgement (NACK) information for one of the two transport blocks;and transmit, via the transmitter, a channel quality control informationalong with the one of the two transport blocks which is retransmittedaccording to the NACK information and a new transport block through thePUSCH to which the HARQ is applied, wherein a number of coded symbols,Q′, required to transmit the channel quality control information iscalculated based on the initial uplink grant, wherein the initial uplinkgrant includes information M_(sc) ^(PUSCH-initial(x)) on the number ofsubcarriers for a transport block for transmitting the channel qualitycontrol information, information C^((x)) on a number of code blocksrelated to the transport block for transmitting the channel qualitycontrol information, and information K_(r) ^((x)) on the size of thecode blocks, and wherein ‘x’ denotes an index of the transport block fortransmitting the channel quality control infolination.
 5. The userequipment according to claim 4, wherein the number of coded symbols, Q′,is calculated by${\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {{initial}{(x)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(x)}}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}^{(x)}}{Q_{m}^{(x)}}}} \right)},$wherein N_(symb) ^(PUSCH-initial(x)) represents a number of singlecarrier-frequency division multiple access (SC-FDMA) symbols per initialPUSCH transmission.
 6. The user equipment according to claim 4, whereinthe processor is further configured to calculate information aboutuplink data retransmitted through the one of the two transport block,wherein the information about the uplink data is calculated by G=N_(L)^((x))·(N_(symb) ^(PUSCH)·M_(sc) ^(PUSCH)·Q_(m) ^((x))−Q_(CQI)−Q_(RI)^((x))).
 7. A method for receiving channel quality control informationthrough a physical uplink shared channel (PUSCH) in a wireless accesssystem that supports hybrid automatic retransmit request (HARQ), themethod performed by a base station and comprising: transmitting aphysical downlink control channel (PDCCH) signal including an initialuplink grant; receiving uplink data using two transport blocks based onthe initial uplink grant; transmitting a negative acknowledgement (NACK)information for one of the two transport blocks; and receiving a channelquality control information transmitted along with the one of the twotransport blocks which is retransmitted according to the NACKinformation and a new transport block through the PUSCH to which theHARQ is applied, wherein a number of coded symbols, Q′, required totransmit the channel quality control information is calculated based onthe initial uplink grant, wherein the initial uplink grant includesinformation M_(sc) ^(PUSCH-initial(x)) on the number of subcarriers fora transport block for transmitting the channel quality controlinformation, information C^((x)) on a number of code blocks related tothe transport block for transmitting the channel quality controlinformation, and information K_(r) ^((x)) on the size of the codeblocks, and wherein ‘x’ denotes an index of the transport block fortransmitting the channel quality control information.
 8. The methodaccording to claim 7, wherein the number of coded symbols, Q′, iscalculated by${\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {{initial}{(x)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(x)}}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}^{(x)}}{Q_{m}^{(x)}}}} \right)},$wherein N_(symb) ^(PUSCH-initial(x)) represents a number of singlecarrier-frequency division multiple access (SC-FDMA) symbols per initialPUSCH transmission.
 9. A base station for receiving channel qualitycontrol information through a physical uplink shared channel (PUSCH) ina wireless access system that supports hybrid automatic retransmitrequest (HARQ), the base station comprising: a receiver; a transmitter;and a processor configured to receive the channel quality controlinformation, wherein the processor is configured to: transmit, via thetransmitter, a physical downlink control channel (PDCCH) signalincluding an initial uplink grant; receive, via the receiver, uplinkdata using two transport blocks based on the initial uplink grant;transmit, via the transmitter, a negative acknowledgement (NACK)information for one of the two transport blocks; and receive, via thereceiver, a channel quality control information transmitted along withthe one of the two transport blocks which is retransmitted according tothe NACK information and a new transport block through the PUSCH towhich the HARQ is applied, wherein a number of coded symbols, Q′,required to transmit the channel quality control information iscalculated based on the initial uplink grant, wherein the initial uplinkgrant includes information M_(sc) ^(PUSCH-initial(x)) on the number ofsubcarriers for a transport block for transmitting the channel qualitycontrol information, information C^((x)) on a number of code blocksrelated to the transport block for transmitting the channel qualitycontrol information, and information K_(r) ^((x)) on the size of thecode blocks, and wherein ‘x’ denotes an index of the transport block fortransmitting the channel quality control information.
 10. The basestation according to claim 9, wherein the number of coded symbols, Q′,is calculated by${\min\left( {\left\lceil \frac{\left( {O + L} \right) \cdot M_{sc}^{{PUSCH} - {{initial}{(x)}}} \cdot N_{symb}^{{PUSCH} - {{initial}{(x)}}} \cdot \beta_{offset}^{PUSCH}}{\sum\limits_{r = 0}^{C^{(x)} - 1}K_{r}^{(x)}} \right\rceil,{{M_{sc}^{PUSCH} \cdot N_{symb}^{PUSCH}} - \frac{Q_{RI}^{(x)}}{Q_{m}^{(x)}}}} \right)},$wherein N_(symb) ^(PUSCH-initial(x)) represents a number of singlecarrier-frequency division multiple access (SC-FDMA) symbols per initialPUSCH transmission.